Power Transformer For Minimum Noise Injection In Between Primary And Secondary Winding &#34;Rompower Active Shield&#34;

ABSTRACT

A system for reducing common-mode noise includes a switch mode power supply having primary and secondary sides, primary and secondary side grounds, an input voltage source, a primary switch, a transformer, a core, and a power output. The primary and secondary sides each have a quiet termination. The transformer includes a primary winding, a secondary winding, and an active shield winding between the primary and secondary windings. The active shield winding has two terminations, is wound in a same direction as the secondary winding, and occupies a same axial position on the core as the secondary winding. One of the terminations of the active shield winding is connected to the quiet termination of the primary side, so that the terminations of the secondary winding and the active shield winding that are adjacent each other carry alternating voltages of a same polarity and a same amplitude.

CROSS-REFERENCE TO RELATED APPLICATIONS

This application is a continuation in part of and claims the benefit ofprior U.S. patent application Ser. No. 16/732,240, filed Dec. 31, 2019,which claims the benefit of U.S. Provisional Application No. 62/787,199,filed Dec. 31, 2018, both of which are hereby incorporated by reference.This application also claims the benefit of U.S. Provisional ApplicationNo. 63/213,107, filed Jun. 21, 2021, which is hereby incorporated byreference.

FIELD

This specification relates to power converters and in particular to thereduction of noise emissions or electromagnetic interference (EMI) inswitch mode power supplies or other applications.

BACKGROUND

High Frequency noise, or Electro-Magnetic Interference (EMI), isgenerated by the switching elements in a power converter using anisolated power transformer, via the primary-secondary straycapacitances, either back to the line supplying the SMPS or into theload that it is powering. Such noise is also radiating and may affectany sensitive nearby components and circuits. There are strict conductedand radiated emission standards with which commercial devices have tocomply.

Over the years, engineers developed many solutions to reduceinterference generated by isolated switch mode power supplies whichapply to common mode noise arising from capacitive coupling betweenwindings and between magnetic core and windings associated with thetransformer. Y capacitors are used between primary and secondary sidesto bypass the noise. However, Y capacitors increase the earth leakagecurrent which places a limit on the value of the Y capacitors.

Electrostatic shields are also used to provide a solution to the passageof noise via capacitive displacement currents through the straycapacitance coupling in the transformer. A shield is usually made of anincomplete turn foil or a bobbin-width wire winding. The common modenoise couples across the shield stray capacitance and returns to thecircuit connected to the shield usually the primary ground.

In U.S. Pat. No. 5,990,776, Jitaru describes the problems associatedwith conventional shields, which include an increase of the parasiticcapacitance across the primary winding and secondary winding. Jitaruproposes different techniques to minimize these drawbacks. Jitaru alsooffers some methodologies of shielding which can be applied in planartransformers. In planar transformers, the parasitic capacitances betweenwindings are larger than those in conventional transformers due to thegeometry of the windings. Jitaru also presents different methodologiesfor noise cancellation. Because the shield—or even multipleshields—between primary and secondary windings do not fully cancel thecommon mode current injected into the earth ground, cancellation methodsof the residual noise have to be applied.

There are different methodologies used for the noise cancellation.Besides the methods suggested by Jitaru in the U.S. Pat. No. 5,990,776,there are other techniques such as the one presented in the U.S. Pat.No. 6,549,431. The solutions depicted there may increase the leakageinductance and add cost and complexity.

U.S. Pat. No. 5,724,236 presents a method of noise cancellation in whichthe classical shield is not connected to ground but to an auxiliarywinding which injects a signal via the conventional shield into thesecondary winding, a signal which is designed to be of opposite polarityof the residual noise.

U.S. Pat. No. 8,023,294 presents different methods of noise cancellationin which there is an auxiliary winding to provide noise suppression inantiphase to the common mode noise which reaches the secondary windingand the coupling of this cancellation signal to the secondary winding isnot done through the shield placed in between primary and secondary, asin U.S. Pat. No. 5,724,236, but through other means such as anadditional shield placed in vicinity of the secondary winding or throughthe magnetic core or even through the conductive strap placed around themagnetic core.

U.S. Pat. No. 5,107,411 presents a method of eliminating noise injectionbetween primary and secondary without the use of a shield but rather bycreating an ideal symmetry between the primary and secondary windingsadjacent to each other and in which the primary and secondary windingadjacent to each other carry alternating voltages of the same polarityin the operating conditions. As a result, there is not displacementcurrent through the parasitic capacitance between primary and secondarywindings. This works well if the turns ratio in the transformer, whichis the ratio between the members of turns in primary and secondary, is1:1. In the case of different turn ratios, additional primary orsecondary coils are required in the transformer. The solution from theabove patent does not cover additional noise injection which can comethrough the magnetic core, layout and other coupling into the EMIfilter.

SUMMARY

In an embodiment, a system for reducing common-mode noise includes aswitch mode power supply including primary and secondary sides, primaryand secondary side grounds, an input voltage source, a primary switch, atransformer, a core, and a power output, wherein the primary side andthe secondary side each have a quiet termination wherein the voltagedoes not change with respect to the primary side ground and with respectto the secondary side ground. The transformer includes a primary windingon the primary side connected to the input voltage source via theprimary switch, a secondary winding on the secondary side connected tothe power output via a rectifier means, and an active shield windingplaced between the primary and secondary windings, wherein the activeshield winding has two terminations, is wound in a same direction as thesecondary winding, and occupies a same axial position on the core as thesecondary winding. The active shield winding and secondary winding eachhave a number of turns. One of the two terminations of the active shieldwinding is connected to the quiet termination of the primary side, sothat the terminations of the secondary winding and the active shieldwinding that are adjacent each other carry alternating voltages of asame polarity and a same amplitude. In an embodiment, the number ofturns of the active shield winding is the same as the number of turns ofthe secondary winding. In another embodiment, the number of turns of theactive shield winding is different from the number of turns of thesecondary winding, so as to induce a voltage into the secondary windingwhich has a polarity that is opposite a polarity of a residual commonmode noise injected from the primary winding to the secondary winding.

In an embodiment, a system for reducing common-mode noise includes aswitch mode power supply including primary and secondary sides, primaryand secondary side grounds, an input voltage source, a primary switch, atransformer, a core, and a power output, wherein the primary side andthe secondary side each have a quiet termination wherein the voltagedoes not change with respect to the primary side ground and with respectto the secondary side ground. The transformer includes a primary windingon the primary side connected to the input voltage source via theprimary switch, a secondary winding on the secondary side connected tothe power output via a rectifier means, and an active shield windingplaced between the primary and secondary windings, wherein the activeshield winding has two terminations, is wound in a same direction as thesecondary winding, and occupies a same axial position on the core as thesecondary winding. The active shield winding and secondary winding eachhave a number of turns. One of the two terminations of the active shieldwinding is connected to the quiet termination of the primary side, sothat the terminations of the secondary winding and the active shieldwinding that are adjacent each other carry alternating voltages of anopposite polarity and a same amplitude. In an embodiment, the number ofturns of the active shield winding is the same as the number of turns ofthe secondary winding. In another embodiment, the number of turns of theactive shield winding is different from the number of turns of thesecondary winding, so as to induce a voltage into the secondary windingwhich has a polarity that is opposite a polarity of a residual commonmode noise injected from the primary winding to the secondary winding.

In an embodiment, a system for reducing common-mode noise includes aswitch mode power supply including primary and secondary sides, primaryand secondary side grounds, an input voltage source, a primary switch, atransformer, a core, and a power output, wherein the primary side andthe secondary side each have a quiet termination wherein the voltagedoes not change with respect to the primary side ground and with respectto the secondary side ground. The transformer includes primary windingon the primary side connected to the input voltage source via theprimary switch, a secondary winding on the secondary side connected tothe power output via a rectifier means, and at least two active shieldwindings. The active shield windings are adjacent to the secondarywinding on both sides of the secondary winding, are wound in a samedirection as the secondary winding, occupy a same axial position on thecore as the secondary winding, and each have two terminations. Theactive shield windings and the secondary windings each have a number ofturns. One of the two terminations of each active shield winding isconnected to the quiet termination of the primary side, so that theterminations of the secondary winding and the active shield windingsthat are adjacent each other carry alternating voltages of a samepolarity and a same amplitude. In an embodiment, the number of turns ofthe active shield windings is the same as the number of turns of thesecondary winding. In another embodiment, the number of turns of theactive shield windings is different from the number of turns of thesecondary winding, so as to induce a voltage into the secondary windingwhich has a polarity that is opposite a polarity of residual common modenoise injected from the primary winding to the secondary winding. In yetanother embodiment, the transformer is implemented in a multilayer PCBand, on both sides of the secondary winding, windings on layers of thePCB that are adjacent to the secondary winding mirror the secondarywinding and carry alternating voltages of a same polarity and sameamplitude as the secondary winding. In still another embodiment, thewindings on the layers of the PCB that are adjacent to the secondarywinding are part of the primary winding.

In an embodiment, a system for reducing common-mode noise includes aswitch mode power supply including primary and secondary sides, primaryand secondary side grounds, an input voltage source, a primary switch, atransformer, a core, and a power output, wherein the primary side andthe secondary side each have a quiet termination wherein the voltagedoes not change with respect to the primary side ground and with respectto the secondary side ground. The transformer includes primary windingon the primary side connected to the input voltage source via theprimary switch, a secondary winding on the secondary side connected tothe power output via a rectifier means, and at least two active shieldwindings. The active shield windings are adjacent to the secondarywinding on both sides of the secondary winding, are wound in a samedirection as the secondary winding, occupy a same axial position on thecore as the secondary winding, and each have two terminations. Theactive shield windings and the secondary windings each have a number ofturns. One of the two terminations of each active shield winding isconnected to the quiet termination of the primary side, so that theterminations of the secondary winding and the active shield windingsthat are adjacent each other carry alternating voltages of an oppositepolarity and a same amplitude. In an embodiment, the number of turns ofthe active shield windings is the same as the number of turns of thesecondary winding. In another embodiment, the number of turns of theactive shield windings is different from the number of turns of thesecondary winding, so as to induce a voltage into the secondary windingwhich has a polarity that is opposite a polarity of residual common modenoise injected from the primary winding to the secondary winding.

In an embodiment, a system for reducing common-mode noise includes aswitch mode power supply including primary and secondary sides, primaryand secondary side grounds, an input voltage source, a primary switch, amultilayer PCB transformer having a planar magnetic core with multiplelegs, and a power output, wherein the primary side and the secondaryside each have a quiet termination wherein the voltage does not changewith respect to the primary side ground and with respect to thesecondary side ground. The transformer includes a primary winding on theprimary side, which primary winding encircles the multiple legs of theplanar magnetic core and is connected to the input voltage source viathe primary switch of the power supply, and a secondary winding on thesecondary side, which secondary winding encircles the multiple legs ofthe planar magnetic core and is connected to the power output via arectifier means. The system further includes at least two active shieldwindings, wherein the active shield windings are adjacent to thesecondary winding on both sides of the secondary winding, mirror theadjacent secondary winding, are wound in a same direction as thesecondary winding, have a same number of turns as the secondary winding,and each have two terminations. One of the two terminations of eachactive shield winding is connected to the quiet termination of theprimary side, so that the terminations of the secondary winding and theactive shield windings that are adjacent each other carry alternatingvoltages of a same polarity and a same amplitude. In an embodiment, theactive shield windings is connected to the quiet termination of theprimary side via an auxiliary winding around one of the legs of theplanar magnetic core, and the auxiliary winding induces a voltage intothe active shield windings which has a polarity that is opposite apolarity of a residual common mode noise injected from the primarywinding to the second winding.

The most traditional technique in preventing noise injection from theprimary winding to the secondary winding of a transformer, techniqueused in switch mode power supply is the placement of an electrostaticshield formed by an incomplete turn of copper foil placed in between theprimary winding and secondary winding. This electrostatic shield isusually connected to the input ground directly or via a ferrite bead orto the high voltage rail where the primary winding is connected intopologies such as flyback or single ended forward. In between theprimary windings and also between secondary winding and theelectrostatic shield there are parasitic capacitances which generatedisplacement currents during the operation. In this patent we will referto one application of the isolated transformer which is a flybackconverter though the methodology described in this patent can be appliedto any transformer and any topology. Further, for simplicity we willpresent a simple non interleaved transformer structure having a primarywinding and a secondary winding and in some cases some additionalauxiliary windings. The embodiments of this patent application areapplied to any transformer structure, such as interleaved or multipleinterleaved wherein the primary and secondary windings are placedalternatively on the bobbin.

There are several ways the noise generated by the voltage swing acrossthe primary switch in a flyback converter and actually in any powerconverter leads to displacements current into the secondary winding viathe parasitic capacitances between primary and secondary winding. Onepath of the noise injection from primary to secondary winding is via thecore of the transformer. The primary winding will inject noise into themagnetic core via the parasitic capacitance between the primary windingand the core and further via the magnetic core this noise is injectedinto the secondary winding. To address that it is common practice thatin the power transformer to place a shield in between the magnetic coreand the primary winding.

Another source of noise injection is caused by the secondary windingvoltage swing, which generates displacement currents via the parasiticcapacitance towards the copper shield and further into the primaryground where the shield is connected. Though the voltage swing in thesecondary winding it is not as big in amplitude as the voltage swing inthe primary winding in many applications, this source of noise can bestill high to prevent the EMI test results to be within 6 dB under theEN 55022 class B limit, such is the case in this particular application.The embodiments presented in this patent will present solutions whichwill eliminate the noise injection from the secondary winding into theshield and further into the primary ground.

The above provides the reader with a summary of some embodimentsdescribed below. Simplifications and omissions are made, and the summaryis not intended to limit, define, or focus the disclosure or claims inany way. Similarly, some parts of the detailed description and drawingsare specifically summarized above, but nonetheless, the summary is notintended to limit, define, or focus the disclosure or claims in any way.Rather, this summary merely introduces the reader to some aspects ofsome embodiments in preparation for the detailed description thatfollows.

BRIEF DESCRIPTION OF THE DRAWINGS

Referring to the drawings:

FIG. 1A depicts a power train of a flyback converter with a “low sidesecondary rectifier”;

FIG. 1B depicts equations associated with the circuit from FIG. 1A;

FIG. 2 depicts two waveforms from the circuit presented in FIG. 1A;

FIG. 3A depicts a power train of a flyback converter with a “high sidesecondary rectifier”;

FIG. 3B depicts equations associated with the circuit from FIG. 3A;

FIG. 4A depicts a power train of a flyback converter with a “high sidesecondary rectifier” and the active shield;

FIG. 4B depicts equations associated with the circuit from FIG. 4A;

FIG. 5A depicts a power train of a flyback converter with a “low sidesecondary rectifier” and an active shield;

FIG. 5B depicts equations associated with the circuit from FIG. 5A;

FIG. 5C depicts a power train of the flyback converter a “low sidesecondary rectifier” and an active shield, wherein the displacementcurrent in between the active shield winding and the secondary windingis zero by injecting between the active shield winding and the secondarywinding displacement currents of the same amplitude and oppositepolarities;

FIG. 5D depicts equations associated with the circuit from FIG. 5C;

FIG. 6A depicts a power train of a flyback converter with a “high sidesecondary rectifier” and a dual active shield;

FIG. 6B depicts a winding arrangement in a transformer bobbin;

FIG. 7A presents a noise cancellation technique by adding fractionalturns;

FIG. 7B presents a noise cancellation technique by subtractingfractional turns;

FIG. 8 presents an embodiment applied to a planar transformer;

FIG. 9A presents an embodiment in which the displacement current betweenthe active shield and the primary winding is minimized;

FIG. 9B presents an embodiment in which the primary winding incorporatedin two layers of a PCB is a total mirror of the secondary windingadjacent to the primary winding and there is no displacement currentbetween primary and secondary winding;

FIG. 9C presents an embodiment in which the primary winding also has therole of an active shield;

FIG. 10A presents EMI test results for a 30 W flyback converter using atransformer with no shield between the primary and secondary windings;

FIG. 10B depicts a bobbin of the transformer used in the EMI testpresented in FIG. 10A just before the secondary winding is wound;

FIG. 11A depicts EMI test results for a 30 W flyback converter using atransformer with one conventional foil copper shield between the primaryand secondary windings;

FIG. 11B depicts a bobbin of the transformer used in the EMI testpresented in FIG. 11A just, after the copper foil shield is placed andbefore the secondary winding is wound;

FIG. 12A depicts EMI test results for a 30 W flyback converter using atransformer with the active shield;

FIG. 12B depicts a bobbin of the transformer used in the EMI testpresented in FIG. 12A, just after the active shield is placed and beforethe secondary winding is wound;

FIG. 13 depicts EMI test results for a 30 W flyback converter using atransformer with an active shield, wherein the number of turns in theshield is three turns instead of four as the secondary winding;

FIG. 14 depicts EMI test results for a 30 W flyback converter using atransformer with the active shield, wherein the number of turns in theshield is five turns instead of four turns as the secondary winding;

FIG. 15A depicts a magnetic core structure using four identical posts;

FIG. 15B presents a vertical cross-section of the magnetic structure ofFIG. 15A;

FIG. 15C presents a power train and a transformer structure for a “lowside secondary rectifier” and an active shield;

FIG. 15D presents primary winding for the magnetic structure of FIG.15A;

FIG. 15E presents the secondary winding and the active shield windingfor the magnetic structure from FIG. 15A;

FIG. 16A presents an interleaved magnetic structure using two activeshield winding and split primary winding configuration;

FIG. 16B presents EMI test results of a flyback converter using aflyback transformer as in FIG. 16A;

FIG. 16C presents EMI test results of a flyback converter using aflyback transformer as in FIG. 16A and with N3′ is seven turns;

FIG. 17A presents an interleaved magnetic structure using twointerleaved shield winding wherein the second active shields connected;

FIG. 17B presents EMI test results of a flyback converter using aflyback transformer as in FIG. 17A and with N3′ is six turns and N3″ isseven turns;

FIG. 18 depicts the power train of the flyback converter with a lowrectifier and two partial shields;

FIG. 19 depicts the power train of the flyback converter with a highrectifier and two partial shields;

FIG. 20 depicts the power train of the flyback converter with a lowrectifier and one partial shield and one noise injection winding;

FIG. 21 depicts the power train of the flyback converter with a lowrectifier and one partial shield and one noise injection winding;

FIG. 22 depicts the power train of the flyback converter with highoutput rectifier and interleaved configuration and two partial shields;

FIG. 23 depicts the Embodiment No. 5, implementation in a bobbin; and

FIG. 24 depicts the transformer drawing of the Embodiment No. 5.

DETAILED DESCRIPTION

In FIG. 1A is presented a flyback converter having an input voltagesource, Vin, 10, a primary switch, 54, a control signal Vc,50, whichcloses and opens the switch S, a transformer Tr1, 52, composed by aprimary winding 30, a secondary winding 32, and a magnetic core 34. Inthe secondary there is a rectification means, 28, which can be a diodeor a synchronized rectifier, and an output capacitor Co, 16. Forsimplicity in this specification the rectification means has a cathodeand an anode. In the event a synchronized rectifier is used the cathodeof the rectifier means is the drain of the Mosfet and the anode of therectification means is the source of the Mosfet. There is a primary sideground, 12 and a secondary side ground, 14. In between primary side andsecondary side there is a Y capacitor Cy, 26 and a parasitic capacitorCp, 22, between the primary ground 12 and the electrical earth 24. Thereis a parasitic capacitor Cs between the secondary ground, 14 and theelectrical earth, 24. In some cases this capacitance is shorted out by adirect electrical connection between the secondary ground and earthground.

In between primary winding, 30 and secondary winding 32, there areparasitic capacitances. The model is simplified, using just twoparasitic capacitances at the terminations of the primary and secondarywindings, C1, 42 and Cn, 46.

In FIG. 2 are presented two key waveforms in the flyback topology, V(S)which is the voltage across the primary switch S, and the controlvoltage Vc, 50. The voltage across the primary switch V(S) does haveseveral transitions. For simplicity, focus on the transition when theprimary switch is closed. At that time the voltage across S, 54, startdecreasing from a high voltage level which in discontinuous mode flybackis the input voltage Vin, after the natural ringing caused by theresonance in between the inductance of the primary winding and theparasitic capacitance reflected across the primary switch, amortizes.The time interval when both switchers, S, 54 and the outputrectification means, 28 are not conducting, is referred in thisspecification as dead time. The primary winding has two terminations, Aand B. The termination A is connected to the primary switch S and theother termination B is connected to Vin. The secondary winding has alsotwo terminations.

One termination C is connected to the output voltage Vo, 18, and theother termination D is connected to the cathode of the rectifier means,28.

When the primary switch S is closed the voltage in A, starts fallingwith a high voltage slope, and the voltage swing is ΔVA. The other endof the parasitic capacitor C1, 42, is connected to C and the voltage inC does not change in report to the secondary ground GNDs, 14. A currentI1, 38, will start flowing through the capacitor C1, from the secondaryground, 14 via Co, and further through S towards the primary ground, 12.This is referred as a common mode current, which is minimized in orderto meet the EMI requirements. On the other end of the primary winding,in B, the voltage does not change versus input ground, 12. On the otherend of the parasitic capacitance Cn, 46, which is connected to D of thesecondary winding the voltage will go up by a level AVD. As a result ofthe voltage swing in D, a current will start flowing through Cn, 46which is part of the common mode noise between primary ground andsecondary ground. There are many parasitic capacities between primarywinding and secondary winding and the amplitude of the currents throughthese parasitic capacitances will be function of the voltage swings ateach terminal versus input ground and respectively output ground. Forsimplicity, the focus is only on the parasitic capacitances C1, 42 andCn, 46.

In FIG. 1B are presented the formulas describing the displacementcurrent through the parasitic capacities C1, 42 and Cn, 46. In formula 4and 5 of FIG. 1B shows that the displacement current In, and I1 areproportionate with the Vin. A constant K is introduced which isproportionate with the value of the parasitic capacitance C1 and Cn andthe slope of the voltage change.

The circuit configuration of the flyback converter presented in FIG. 1Ais referred in the field as a “low side secondary rectifier”, when theanode of the rectifier means is connected to the secondary ground, 14.

In this configuration the dot, 120, in the secondary winding is placedto the cathode of the rectifier means. The dots placed in the windingsof the transformer represent the polarity of the windings. When avoltage is applied to a winding in a transformer with the positivepolarity at the dot, the rest of the winding will have a positivepolarity induced at the dot as well.

In conclusion, in the configuration from FIG. 1, referred also as a “lowside secondary rectifier” there is a displacement current through theparasitic capacitance between primary winding and secondary winding,displacement current described by the formula 4 and 5 from FIG. 1B. Thisdisplacement current is proportionate with Vin and also with the turnratio.

In FIG. 3A is presented a flyback converter in which the dot end of thesecondary winding is placed to the secondary ground, 14. The transformeritself remains the same, only the rectifier means is connected with itsanode to the termination C of the secondary winding and the terminationD of the secondary winding is connected to the secondary ground 14. Thecircuit configuration of the flyback converter presented in FIG. 3A isreferred in the power conversion field as a “high side secondaryrectifier”.

The flyback converter presented in FIG. 3A works in the same way as theflyback converter presented in FIG. 1A. There is no difference inoperation but there are some clear differences in the displacementcurrents though the parasitic capacitances in between primary winding 30and secondary winding 32.

In the termination A, at the time when the primary switch closes thevoltage will decay by ΔVA versus the primary ground 12. In thetermination C of the secondary winding the voltage will decay by ΔVCversus the secondary ground 14. A displacement current I1, 38 will becreated through the parasitic capacitance C1, 42. The value of thedisplacement current I1 is depicted by the equation 4 from FIG. 3B,I1=k*Vin*((N−1)/N). In the case in which N=1, which means the number ofturns in primary is equal to the number of turns in the secondary, thedisplacement current I1 is zero.

In termination B of the primary winding the voltage does not changeversus primary ground. In termination D of the secondary winding thevoltage does not change either versus secondary ground. In conclusionthe displacement current In, through Cn, 46 is zero.

In the configuration presented in FIG. 3A, the displacement currentthrough Cn is always zero and the displacement current through C1 issmaller than the displacement current from the configuration in FIG. 1.More than that in the event in which N=1 there is no displacementcurrent because the terminations of the primary winding and secondarywinding, swing with the same polarity. A quiet connection is aconnection in which the voltage does not change when S closes or opens.Such a quiet connection is +HV, 90, GNDp,12, GNDs,14 and Vo,18. Thetermination B and D in FIG. 3A and termination B and C in FIG. 1A areplaced to a quiet connection.

In the circuit presented in FIG. 3A the termination of the primarywining, A, and the termination of the secondary winding, C do move inthe same direction versus the primary and respectively secondary groundwhen the switch S is closed and opened.

In conclusion the flyback converter configuration depicted in FIG. 3A isquieter in respect of noise injection from primary to secondary, via theparasitic capacitance between primary winding and secondary winding,than the configuration depicted in FIG. 1A. When ultrafast rectifiers orSchottky diodes were used for the rectifier means, 28, the utilizationof the “the high side secondary rectifier” it was a relatively easyimplementation. In the recent application in which synchronizedrectification is used, the “high side secondary rectifier” becomes morechallenging because the Mosfet used for synchronized rectifier has to bedriven at the high side. In the case of synchronized rectificationutilization of the output rectifier the implementation depicted in FIG.1A is easy to implement because the gate of the mosfet which is used assynchronized rectifier is driven from the ground level.

Some of the embodiments herein make the use of a Mosfet as synchronizedrectifier easy and the Mosfet will be driven from the ground level whilestill benefiting of zero displacement current as is achieved in FIG. 3Awhen N=1.

By analyzing the displacement current through the parasitic capacitancesin the transformer Tr1, 52 in configuration from FIG. 1A and FIG. 3A itshows clearly that at high side secondary rectifier has lowerdisplacement current thought the parasitic capacitance between primaryand secondary winding. More than that for a transformer with a turnsration N=1 there is zero displacement current through the parasiticcapacitances from primary to secondary winding of the transformer, whichvalidates the main embodiment of the U.S. Pat. No. 5,107,411. Thedifference in EMI behavior between the high secondary rectifier and thelow secondary rectifier is known by the experts in the field. Thisanalysis was done in this patent in order to introduce an analysismethodology for underlining the key advantages of the main embodimentsof this invention over the prior art.

The most traditional technique in preventing noise injection from theprimary winding to the secondary winding of a transformer, techniqueused in switch mode power supply is the placement of a electrostaticshield formed by an incomplete turn of copper foil placed in between theprimary winding and secondary winding. This electrostatic shield isusually connected to the input ground directly or via a ferrite bead orto the high voltage rail where the primary winding is connected intopologies such as flyback or single ended forward. In between theprimary windings and also between secondary winding and theelectrostatic shield there are parasitic capacitances which generatedisplacement currents during the operation. This specification generallyrefers to one application of the isolated transformer which is a flybackconverter though the methodology described in this specification can beapplied to any transformer and any topology. Further, for simplicity,the specification initially presents a simple non interleavedtransformer structure having a primary winding and a secondary windingand in some cases some additional auxiliary windings. The embodiments ofthis specification are applied to any transformer structure, such asinterleaved or multiple interleaved in which the primary and secondarywindings are placed alternatively on the bobbin.

In FIG. 10A is presented the EMI test results of a 30 W flybackconverter having a non-interleaved transformer using a RM8 type magneticcore and having an EMI filter designed to filter the differential andcommon mode noise. In FIG. 10B is presented the bobbin on which theprimary winding is placed followed by an isolator and further thesecondary winding will be placed. This experiment has 18 turns inprimary and 4 turns in secondary. The test results are for Vin=230 Vac @50 hz for an output voltage of 12V @ 2.5 A and the plot from FIG. 10A isthe QPEAK and the limits are based on the EN 55022 class B. It isvisible than in some frequency ranges the violation of the limit is morethan 15 dB.

In FIG. 11A is presented the EMI measurements results after one openturn copper shield is connected to primary ground is placed in betweenthe primary and secondary, copper shield depicted in FIG. 11B. After thecopper shield is placed the EMI level did decrease by 10dB in somefrequency ranges. The expectations were that the impact of the shieldwould have been more significant because the shield would prevent thedisplacement current through the parasitic capacitance between theprimary and secondary winding. Analyzing the reasons why the traditionalcopper foil shield which is Prior Art is not as effective as expected itwill lead us to the embodiments of this specification. The embodimentswithin the scope and spirit of this specification improve significantlythe noise reduction of the shield.

There are several ways the noise generated by the voltage swing acrossthe primary switch in a flyback converter and actually in any powerconverter, reaches the secondary. The voltage swing in the primarywinding leads to displacements current into the secondary winding viathe parasitic capacitances between primary and secondary winding.Another path of the noise injection from primary to secondary winding isvia the core of the transformer. The primary winding will inject noiseinto the magnetic core via the parasitic capacitance between the primarywinding and the core and further via the magnetic core this noise isinjected into the secondary winding. To address that is common practicethat in the power transformer a shield is placed in between the magneticcore and the primary winding. In most of the Prior Art the shield ismade of a foil of copper which form an open turn in the transformer. Inother Prior Art, the shield is formed by a wire wound layer of copperwire with one of the terminal not connected and another terminalconnected to a primary ground or to DC input voltage, +HV, 90.

Another source of noise injection is caused by the secondary windingvoltage swing, which generates displacement currents via the parasiticcapacitance towards the copper shield and further into the primaryground or +HV, 90 where the shield is connected. Though the voltageswing in the secondary winding is not as big in amplitude as the voltageswing in the primary winding in many applications, this source of noisecan be still high preventing the EMI test results to be within 6dB underthe EN 55022 class B limit, such is the case in this particularapplication mentioned in the specification. The embodiments presented inthis specification will present solutions which will eliminate the noiseinjection from the secondary winding into the shield and further intothe primary ground.

In FIG. 4A is presented the flyback converter using a transformer Tr2,68 with a primary winding 30 with two termination A and B, wherein Atermination is connected to the primary switch, 54, and the Btermination at the dot is connected to the Vin, 10, which is alsolabeled as +HV, 90. There is also a secondary winding with twoterminations, a termination D at the dot, connected to secondary ground14 and another termination, C connected at the anode of the rectifiermeans. In addition to these two main windings there is an active shieldwinding, 80 which has the number of turns N2′ and wound in the samedirection as the secondary winding. The active shield, 80, has twoterminations, K and M. The K termination is placed to a quietconnection, +HV,90, and the M termination, of the active shield, 80, isnot connected. The winding, 80, is referred in this specification as anactive shield winding because acts as a shield and in the same time theactive shield winding move with the same polarity and amplitude as theadjacent secondary winding preventing any displacement current to flowthrough the parasitic capacitances between secondary winding and theactive shield winding. It can be built with exactly the same winding asthe secondary winding or by using several stands of thinner wire inparallel to reduce its width and as a result reduce the leakageinductance between primary and secondary.

In between the active shield 80, and the primary winding, 30, there areparasitic capacitances. For simplicity, the specification defines justC1′, 70, in between the primary winding located to the termination A,and the active shield winding, 80, located to the termination M, and C′nin between the primary winding located to the termination B, and theactive shield winding, 80, located to the termination K.

In between the active shield 80, and the secondary winding, 32, thereare parasitic capacitances. For simplicity, the specification definesjust C1″, 60, in between the secondary winding located to thetermination C, and the active shield winding, 80, located to thetermination M, and C″n in between the secondary winding located to thetermination D, and the active shield winding, 80, located to thetermination K.

When the primary switch 54, is closed the voltage in A terminal of theprimary winding will start decreasing rapidly versus the input ground,12. The voltage in the terminal B of the primary winding does notchange. The voltage in K of the active shield winding does not changebeing connected to a quiet connection, which is the +HV. The voltage inM does change by ΔVM going lower versus the primary ground 12. A currentwill be produced through the parasitic capacitance between primarywinding 30, and active shield winding, 80, displacement current which isproportionate by the difference in between ΔVA and ΔVM. The displacementcurrent though C1′, 70 is presented in formula 2 from FIG. 4B. Thedisplacement current through Cn′ is zero because both ends of theparasitic capacitor Cn′ do not swing being connected to a quietconnection, +HV,90. It is mentioned that I1′ displacement current andI′n displacement current flow from the primary ground to the primaryground and is not part of the common mode noise. These displacementcurrents will impact the “effective capacitance” reflected across theprimary switch S. In hard switching operation of the converter that willincrease the switching losses, and in soft switching operation of theconverter will require more energy to discharge the parasiticcapacitance across the primary switch before the primary switch turnson. In the event N′2 is equal with N1, the I′1=0. In such a case, theeffective capacitance reflected across the primary switch is reduced tothe static parasitic capacitance across the main switch.

The static parasitic capacitance in the winding is the physicalcapacitance which is measured in a static mode when there is not ACvoltage present across the windings. The effective capacitance isdefined by the displacement current caused by the movement of thewinding towards each other when ac voltages are present across thewindings.

When the primary switch closes the voltage in termination D of thesecondary winding 32 does not change being connected to the secondaryground 14. The voltage in terminal C of the secondary winding does swinglower reported to the secondary ground by ΔVC. In equation 3 and 4 fromFIG. 4B is concluded that displacement currents between secondarywinding, 32 and the active shield, 80, via, C1″,60 and Cn″, 62 are zeroif N′2=N2. That means that in the configuration depicted in FIG. 4A ifthe number of turns in the active shield has the same number of turns asthe secondary winding, N2=N2′, then the displacement current in betweenthe active shield winding and the secondary winding is zero. Inconclusion there is not displacement current between the secondarywinding and the active shield winding. Because the active shieldwinding, 80 is connected to the input ground, there is not displacementcurrent between secondary ground and the primary ground. The activeshield winding has the role of an electrostatic shield and because thewindings which form the active shield 80, move with the same polarityand the same amplitude as the secondary winding there is no common modenoise. For an ideal operation the secondary windings and the activeshield winding shall be identical, which can be easily implemented in amultilayer PCB planar magnetic.

In wire wound transformers the active shield,80, shall be implemented byusing multiple strands in parallel of thin wire with the same number ofturns as the secondary winding. The thin wire used in multiple strandsin parallel will decrease the distance in between the primary andsecondary winding and in this way will decrease the leakage inductancebetween primary winding and secondary winding. The multiple strands ofwire used for the active shield will cover the entire winding area inthe bobbin covering fully the secondary winding. The use of thin wire inthe active shield will also decrease the eddy current losses in theshield. In FIG. 12B is presented such an implementation of the activeshield winding. A method of reducing common-mode noise in a switch modepower supply; the switch mode power supply having a primary side and asecondary side, a primary side ground and a secondary side ground, theprimary side and the secondary side having a quiet termination whereinthe voltage does not change versus the input ground and versus secondaryground during the operation of the switch mode power supply, and furtherhaving an input voltage source, at least one primary switch, atransformer and a power output; the transformer having at least aprimary winding in the primary side, of the power supply and connectedto the input voltage source via the primary switch, and at least onesecondary winding of the transformer on the secondary side of the powersupply, and the secondary winding connected to the power output via atleast one rectifier means, at least one active shield winding placed inbetween the primary winding and the secondary winding having the samenumber of turns as the secondary winding and wounded in the samedirection as the secondary winding, the active shield windings havingtwo terminations and occupy the same axial position on the core as thesecondary winding; and one termination of the active shield is connectedto the primary quiet termination so that in operation allcorrespondingly adjacent the terminations of the secondary winding andthe active shield winding carry alternating voltages of the samepolarity and same amplitude.

In the configuration depicted in FIG. 4A zero displacement currentbetween the parasitic capacitance between active shield and thesecondary winding can be achieved. Because the active shield, 80, isconnected to a quiet connection +HV, 90, further connected to theprimary ground, zero common mode noise is flowing through the primaryand the secondary ground.

FIG. 5A presents a flyback converter using the “low side outputrectifier” configuration in which the secondary winding has the dot tothe cathode of the rectifier means. The transformer Tr2, 68 from FIG. 5Ahas the same windings as the transformer presented in FIG. 4A. Thedifference is that the active shield winding, 80 is connected to theinput ground, 12 at the terminal M. In the secondary the D terminal ofthe secondary winding 32 is connected to the cathode of the rectifiermeans and the C terminal of the secondary winding is connected to theVo+, 18.

At the time when the primary switch S is closed the voltage intermination A of the primary winding start decreasing towards inputground, 12 by an amplitude ΔVA. The voltage at the terminal M of theactive shield winding, 80 does not move in reference to input ground.The current through the parasitic capacitance C1′ is described by theequation 1 from FIG. 5B.

The current through the parasitic capacitance Cn′ is described by theequation 2 of FIG. 5B.

The voltage in termination C of the secondary winding does not changewhen S is closed, and neither the voltage in termination M of the activeshield winding. In the termination K of the active shield winding andthe voltage in termination D of the secondary winding move with the samepolarity and because N′=N2 and the current through Cn″ is zero asdescribed by the equation 4, for N′2=N2 from FIG. 5B.

Regardless of the configuration of the flyback converter, such is the“low side secondary rectifier” as depicted in FIG. 5A or the “high sidesecondary rectifier” configuration as depicted in FIG. 4A, thetransformer Tr2, 68 using the active shield winding there is not commonmode noise from the primary to the secondary of the transformer forN′2=N2.

In FIG. 5C is presented another structure with low side secondaryrectifier but with the dot of the shield winding at the terminal M andthe connection to the quiet spot is done at the terminal K and not in atthe terminal M as is done in FIG. 5A. The currents through the parasiticcapacitances C″1 and C″n are depicted in formula 1 and 2 from FIG. 5D.The displacement current In″ is induced from the secondary into theprimary ground via Cn″ and the displacement current I1″ is induced fromthe primary, via the active shield 80, into the secondary ground viaC1″. In formula 3 from FIG. 5D is depicted the common mode current whichis the difference between I″n and I″1. In the event that N2′=N2 thecommon mode noise is zero. Unlike the embodiment presented in FIG. 5A inwhich the displacement current through the parasitic capacitances inbetween the active shield windings and the secondary windings is zerobecause the voltage on the active shield windings and the voltage on thesecondary windings adjacent to each other move with the same polarityand the same amplitude, in the embodiment presented in FIG. 5C there isdisplacement current through the parasitic capacitances between activeshield winding and the secondary winnings but the displacement currentinduced at each termination of the active shield winding and thesecondary winding is of the same amplitude but of opposite polarity andthey cancel and the common mode current from the primary ground to thesecondary ground is zero.

This discloses a system and method of reducing common-mode noise in aswitch mode power supply; the switch mode power supply having a primaryside and a secondary side, a primary side ground and a secondary sideground, the primary side and the secondary side having a quiettermination in which the voltage does not change versus the input groundand versus secondary ground during the operation of the switch modepower supply, and further having an input voltage source, at least oneprimary switch, a transformer and a power output; the transformer havingat least a primary winding in the primary side of the power supply andconnected to the input voltage source via the primary switch, and atleast one secondary winding of the transformer on the secondary side ofthe power supply, and the secondary winding connected to the poweroutput via at least one rectifier means, at least one active shieldwinding placed in between the primary winding and the secondary windinghaving the same number of turns as the secondary winding and wounded inthe same direction as the secondary winding, the active shield windingshaving two terminations and occupy the same axial position on the coreas the secondary winding; and one termination of the active shield isconnected to the primary quiet termination so that in operation allcorrespondingly adjacent the terminations of the secondary winding andthe active shield winding carry alternating voltages of the oppositepolarity and same amplitude.

The configurations from FIG. 5A and 5C lead to the same results thoughthe dot position in the active shield winding and the connection to thequiet connection are different. This configuration is another keyembodiment of this invention.

This configuration is suitable in the event noise cancellation isnecessary. Noise cancellation is a signal cancellation technique inwhich a signal is injected via the path between primary ground andsecondary ground, signal injection which has the same amplitude but theopposite polarity of the common mode noise. This specification refers tothe technique of signal cancellation as a noise cancellation. By tuningthe number of turns in the active shield winding noise is injected inbetween primary to secondary ground via the parasitic capacitancesbetween the active shield winding and the secondary winding, with apolarity controlled by the positive or negative sign of the flowingexpression (N2−N2′). The amplitude of the noise injection is done by thedifference between N2 value and N2′ value.

If the number of turns in the active shield winding is different thanthe number of turns in the secondary winding, then the displacementcurrent through the parasitic capacitance in between the active shieldwinding and the secondary winding is not zero, which means that commonmode noise will be injected, common mode noise of a given polarity and agiven amplitude function of the difference of turns between the activeshield winding and the secondary winding. This displacement current canbe utilized for the purpose of noise cancellation.

The common mode noise in between primary and secondary of a converter istransferred not only through the parasitic capacitance between theprimary winding and secondary winding. As previously mentioned it can betransferred via the parasitic capacitance between the windings, primaryand secondary winding and the magnetic core of the transformer. Thereare also other path of common mode noise transferred, via layout, andcoupling between the converter components. In such cases having zerodisplacement current via the parasitic capacitance between secondary andprimary winding or via the secondary and active shield winding does noteliminate the common mode noise entirely.

In such cases allowing a controlled displacement current of the rightamplitude and polarity through the parasitic capacitance between activeshield winding and secondary winding can reduce significantly to commonmode noise. In FIG. 16A is depicted a transformer, having interleavedprimary and secondary winding and two active shield windings, N3′ andN3″. The primary winding is placed first on the bobbin, half of primaryforms the first layer, N1, and the other half of primary forms the lastlayer, N1′. In between the primary windings formed by N1 and N1′ thereare placed the active shields N3′ and N3″ and the secondary winding N2,is placed in between the two active shields, N3′ and N3″. Theconfiguration from FIG. 16A is using the embodiment of FIG. 5A, in whichthe active shields windings have the same number of turns as secondarywinding and the voltages on the windings terminations move with the sameamplitude and with the same polarity. For the configuration in whichN1=N1′=11 turns, N3′=N3″=4 turns and N2=4 turns, and using a very smallY cap of 68 pF, the EMI measurements are depicted in FIG. 16B. As isvisible from FIG. 16B the common mode noise exceeds the EN55022 KlasseB, QPEAK limits at several frequencies. Though the displacement currentvia the parasitic capacitance between the active shield windings and thesecondary winding is zero, the common mode noise is not zero, due tonoise penetration via the parasitic capacitance between windings and themagnetic core and other means as previously presented. In such cases thesolution presented in this specification is to control the noiseinjection in the transformer via the parasitic capacitance between theactive shield winding and the secondary winding by tuning the number ofturns in the active shields.

In FIG. 16C are presented the EMI measurement results for theconfiguration from FIG. 16A for the configuration in which N1=N1′=11turns, N3′=7 turns, N3″=4 turns and N2=4 turns. It is visible bycomparing the measurement from FIG. 16C and FIG. 16B, that by using thecontrolled noise injection between active shield winding and thesecondary winding, there is an attenuation of 8 dB and in this modebring the EMI into compliance level.

Another embodiment combines the active shield from the embodimentpresented in FIG. 5A with the active shield embodiment presented in FIG.5C. Such implementation is depicted in FIG. 17A.

In FIG. 17A the active shield, N3′ is in compliance with theconfiguration depicted in FIG. 5A and the shield, N″3 is in compliancewith the configuration depicted in FIG. 5C. The EMI test results fromthe configuration from FIG. 17A, wherein N1=N1′=11 turns, N3′=6 turns,N3″=7 turns and N2=4 turns is presented in FIG. 17B. In thisconfiguration the attenuation is 14dB in comparison with the testresults from configuration from FIG. 16A with the test results from FIG.16B. The test results from the configuration from FIG. 17A which arepresented in FIG. 17B, is passing the EN 55022, Klasse B QPEAK with 8 dBof margin and using a Y capacitor of 68 pF.

This discloses a system and method of reducing common-mode noise in aswitch mode power supply; the switch mode power supply having a primaryside and a secondary side, a primary side ground and a secondary sideground, the primary side and the secondary side having a quiettermination in which the voltage does not change versus the input groundand versus secondary ground during the operation of the switch modepower supply, and further having an input voltage source, at least oneprimary switch, a transformer and a power output; the transformer havingat least a primary winding in the primary side and connected to theinput voltage source via the primary switch of the power supply, and atleast one secondary winding of the transformer on the secondary side ofthe power supply, in which the secondary winding connected to the poweroutput via at least one rectifier means, at least two active shieldswinding adjacent to the secondary winding on both sides of the secondarywinding having the same number of turns as the secondary winding andwounded in the same direction as the secondary winding, and occupy thesame axial position on the core as the secondary winding; and onetermination of each active shield is connected to the primary quiettermination so that in operation all correspondingly adjacent theterminations of the secondary winding and the active shield windingscarry alternating voltages of the same polarity and same amplitude.

As mentioned before the noise injection in the secondary winding doesnot always come from the primary winding via the parasitic capacitancebetween the primary winding and the secondary winding. The embodimentsusing an active shield winding do prevent only this type of noiseinjection. In addition to that, noise can be injected into the secondarywinding from the auxiliary windings when the auxiliary windings areplaced near the secondary winding. In FIG. 6A and FIG. 6B is presentedanother embodiment in which an active shield winding is placed betweenthe primary winding and the secondary winding and another active shieldwinding is placed on top of the secondary winding to prevent noiseinjection from the core or from the auxiliary windings. This embodimentis presented in FIG. 6A and the construction technique is depicted inFIG. 6B. In FIG. 6B on the first layer is placed the primary winding. Onthe second layer is placed the active shield winding in this drawingimplemented by multi-strands of thin wire, the active shield windinghaving the same number of turns as the secondary winding. On the thirdlayer is placed the secondary winding, on the fourth layer is placed theactive shield winding and on the top layer is placed the auxiliarywinding or no other winding function of the application. The purpose ofthis configuration is to shield the secondary windings not only from thenoise generated by the primary windings but also form noise generatedfrom the auxiliary windings.

In additions to the noise injection methodologies based on tuning thenumbers of turns in the active shield versus the number of turns in thesecondary windings, another embodiment uses even fractional turns in theactive shields to adjust the noise suppression signal.

In FIG. 7A and 7B is presented another embodiment in which the number ofturns in the active shield winding varies slightly versus the number ofturns in the secondary winding by using a different number of turns oreven fractional turns to adjust the noise suppression signals.

In FIG. 7A and 7B the magnetic core, 34, has one central post, CP, andfour outer legs, 11, 12, 13 and 14. That allows the use of fractionalturns starting with quarter turn, ¼, and also half turn, ½.

For example for 1 turn secondary in FIG. 7A, the number of turns in theactive shield is modified to be 1.25 turns and in FIG. 7B is modified tobe 0.75 turns.

Because there is not power delivered via the active shield winding thefractional turns can work without the risk of magnetic flux unbalance.In some cases even a larger increment can be used, such as full turns,rather than fractional turns. For example for a 4 turns secondary, thenumber of turns in the active shield can be 3 or 5 turns function of thepolarity of the additional noise injected. In FIG. 13 shows the EMI ifonly 3 turns is used for the active shield and in FIG. 14 if 5 turns areused in the active shield rather than 4 turns as is depicted in FIG.12A. In FIG. 12A when 4 turns are used for the active shield, the samenumbers as the secondary winding, there is a larger amplitude noisearound 1 Mhz caused by the ringing across the main switch during thedead time of the flyback converter. That noise could have been injectedthrough other means rather than the parasite capacitance between primarywinding and secondary wining, such as through the magnetic core. Byplacing 5 turns in the active shield rather than 4 turns a signal ofopposite polarity of the common mode noise was injected from the activeshield to the secondary winding via the parasitic capacitance in betweenthe active shield and secondary winding and that signal did cancel the 1MHz noise as can be seen in FIG. 14.

This discloses a system and method for which the number of turns for theactive shields windings is adjusted in order to create a mismatch to thesecondary winding and induce a voltage into the secondary windingdesigned to be of opposite polarity of the residual common mode noiseinjected from primary to secondary.

In noise cancellation technique in which the number of turns in theshield is tuned to be higher or smaller than the number of turns in thesecondary winding the noise injection from the primary winding to thesecondary winding can be also tuned by partially removing wire woundactive shield allowing the noise from the primary to reach thesecondary.

The embodiments herein can be also used in planar transformers. FIG. 8presents the power train of a flyback converter for which thetransformer winding is embedded in a multilayer PCB. Primary windingsare placed on four layers 892, 894, 802 and 804. The number of turns perlayer may vary function of the application. The secondary windings areplaced on the layer 898. The active shield windings are placed on thelayer 896 and 800, and have to have the same number of turns as thesecondary or can have a slight different number of turns includingfractional turns as described by the embodiment from FIGS. 7A and 7B ifnoise cancellation technique is employed. The secondary winding placedon the layer 898 may be placed on several layers, usually an evennumber. In the event the secondary winding is placed on several layers,the number of turns and the dot (120) for the active shield on layer 896and 800 shall be the same as the secondary layers adjacent to the shieldto comply with the active shield solution from FIG. 4A.

The displacement current between the active shield and the secondarywinnings adjacent to it shall be zero.

Further, in embodiments, the transformer is implemented in a multilayerPCB and the windings on the layers adjacent to the secondary windings,on both side of the secondary winding, are the mirror imagine of thesecondary winding and they carry alternating voltages of the samepolarity and same amplitude as the secondary winding.

In applications in which controlled noise injection is utilized thenumber of turns in the active shields may be different than the numberof turns in the secondary.

In the event the embodiment depicted in FIG. 5C is employed, theconnection to the quiet termination and the dot position for the activeshield shall be in compliance with the concept depicted in FIG. 5C.

FIG. 9A presents another embodiment in which the active shields, onlayer 900 and 996 are adjacent to the secondary windings on layer 998,and the active shields are connected to the quiet end of the primary at+HV, 90. For example if the number of turns of the primary winding perlayer 992 and 994 is just one, and the active shield windings placed onlayer 996 and 900, is also one, the displacement current via theparasitic capacitance between layer 992 and layer 900 and respectivelyfrom layer 994 to 996, is low because the primary windings placed onlayer 994 and 992 have a lower voltage swing being connected closer to+HV. In addition to that the displacement current between primarywindings from layers 992 and 994 and the active shield winding placed onlayer 996 and 900 is in between primary ground to primary ground and itdoes not influence the common mode noise. This displacement current willjust influence the switching losses and impact the efficiency of thepower converter.

In FIG. 9B is presented another embodiment. The secondary windings areplaced on at least two layers, in this case layer 906 and 908. In oneparticular implementation let's consider that the number of turns insecondary is two, one turn per layer 906 and one turn per layer 908 andthese windings are in series, in total two turns. The number of turn'sper layer 992 of the primary winding is one as well and the number ofturns of the primary winding placed on layer 994 is one turn as well. Incases in which the total number of turns in the primary is 12, therewill be 5 turns placed on the layer 902 and 5 turns on the layer 904.For practical purposes more layers can be added for the primary windingwith the goal of decreasing the number of turns per layer for layer 902and layer 904. The primary winding on the layer 992 and on the layer 994in this implementation will have two roles. One role is to be part ofthe primary winding and the second role to be the active shield windingfor the secondary windings placed on layer 906 and 908. This would bethe same implementation as in FIG. 4A with the difference that theactive shield winding is also part of the primary winding. This makesthe active shield winding part of the power train, wherein power istransferred through these winding and also these windings are used asactive shields. The embodiment of FIG. 9B eliminates the need for twoadditional layers wherein to place the active shield winding. In thisexample, one turn per layer in the layers 992, 994, 906 and 908 is used.This embodiment works for any number of turns per layer as long as thenumber of turns per layer in 906 and 994 and respectively per 908 and992 is the same.

Moreover, the windings on the layers adjacent to the secondary windings,are part of the primary windings.

In FIGS. 8, 9A, 9B and 9C is depicted also the magnetic flux B, producedby the current through the primary winding, 101, The arrow line, 102,represents the current flowing through the primary winding. The dottedline per layer 906 and 908, labeled 110, represent the current flow inthe secondary winding after the switch, 54, turns off. This applies onlyfor the flyback topology. The embodiments apply also for any topologysuch as forward derived topologies.

In FIG. 9C is presented another embodiment in which the secondarywinding is placed layer 914, on one or several layers. In this case theprimary winding adjacent to the secondary winding placed on layer 992and layer 994 are in parallel unlike the structure depicted in FIG. 9Bin which the primary winding 992, and 994 which act as active shield areplaced in series. The primary windings 992 and 994 and have the samenumber of turns as the secondary windings and are placed on the adjacentlayers to the secondary windings 914. Like in FIG. 9B the primarywinding on layer 994 and layer 992 takes the role of the active shield.This is done by having the primary winding adjacent to the secondarywinding to have the same number of turns as the secondary winding andthe voltage swing is in such way that the displacement current throughthe parasitic capacitance between 994 and 914 and 992 and 914 is zero.In additional to that the primary winding which takes the role of theactive shield are also connected to the quiet termination. The winding992 is connected to HV+ and the winding 994 is connected to +HV as well.The embodiment described in FIGS. 9B and 9C is suitable for multilayerplanar transformer because additional layers are not needed just for theactive shield windings. For example in FIG. 9B 4 layers are allocatedfor the primary winding and two layers for the secondary winding, intotal only 6 layers instead of eight layers if the embodiment describedin FIG. 8 and FIG. 9A would be used.

The embodiments within the spirit and scope of this specification areapplicable also in the more complex magnetic structures as the onepresented in U.S. Application Publication No. US 2016/0307695 entitled“Magnetic Structures for Low Leakage Inductance and Very HighEfficiency.”

In FIG. 15A is presented a horizontal cross-section through a multi-legmagnetic structure presented in the “Magnetic Structures for Low LeakageInductance and Very High Efficiency” patent application. The magneticstructure depicted in FIG. 15A contains has four legs, 150,152,154 and156 and two plates 158 and 160, as is depicted also in the verticalcross-section of this magnetic structure in FIG. 15B. The primarywinding is wound around the four legs as depicted in FIG. 15D. Themagnetic field through each leg has an opposite polarity to the legsadjacent to it. This magnetic structure is suitable for flybacktransformer and also for forward derived transformer. The leakageinductance between primary winding and secondary winding becomes verysmall which makes this transformer structure suitable for flybackapplications. In addition to that the number of layers in suchstructures can be reduced and the volume of the magnetic core is smallerthan for independent transformers which will reduce the core loss.

In FIG. 15C is presented the simplified schematic of a flyback topologyemploying an active shield using the concept depicted in FIG. 5A. InFIG. 15E are presented four layers of the multilayer transformer usingthe magnetic core structure from FIG. 15A. As presented in FIG. 15E thesecondary windings are implemented in two inner layers, Lsec1 and Lsec2.The shield layers are placed on two layers Lshield1 and Lshield adjacentto the layers in which the secondary windings are embedded. Thesecondary winding starts from Lsec1 layer, from X2 termination and endson Lsec2 layer, to the termination X1 with the interconnection betweenlayers X3. X1 termination is connected to the Vo, 18 and X2 terminationis connected to the cathode of the synchronized rectifier 28. The activeshield starts from YM connection on Lshield2 layer and ends on Lshield1layer at YK with the interconnection between layersY1. The shieldwinding on Lshield1 is the mirror imagine of the secondary winding onLsec1 layer and the shield winding on Lshield 2 is the mirror imagine ofthe secondary winding Lsec2. The voltage in the termination YK of theshield winding and the voltage in the termination X2 of the secondarywinding move with the same polarity and the same amplitude. Thetermination YM of the shield winding and the termination X1 of thesecondary winding are both connected to a quiet termination, GNDp, 12and respectively Vo, 18, as in the configuration from FIG. 5A. If noiseinjection is necessary, the termination YM of the active shield will notbe connected directly to GNDp, 12. It will be connected to an auxiliarywindings of one or more turns wound around one of the four legs and thatauxiliary winding termination not connected to the active shield will beconnected to the GNDp, 12. The winding direction of the auxiliarywinding is chosen to inject a signal in the shield of a polaritydesigned to reduce the common mode noise. The number of turns for theauxiliary winding will be chosen to have the voltage amplitude that thenoise injection via the shield into the secondary winding will reducethe common mode noise.

In an embodiment, a system and method of reducing common-mode noise in aswitch mode power supply includes the switch mode power supply having aprimary side and a secondary side, a primary side ground and a secondaryside ground, the primary side and the secondary side having a quiettermination in which the voltage does not change versus the input groundand versus secondary ground during the operation of the switch modepower supply, and further having an input voltage source, at least oneprimary switch, a multilayer PCB transformer having a planar magneticcore with multiple legs, and a power output; the transformer having atleast a primary winding in the primary side, the primary windingencircling the multiple legs of the planar magnetic core and connectedto the input voltage source via the primary switch of the power supply,and at least one secondary winding of the transformer, the secondarywinding encircling the multiple legs of the planar magnetic core, on thesecondary side of the power supply, wherein the secondary windingconnected to the power output via at least one rectifier means; at leasttwo active shields winding adjacent to the secondary winding on bothsides of the secondary winding the active shields winding are the mirrorimagine of the secondary winding adjacent to them having the same numberof turns as the secondary winding and wounded in the same direction asthe secondary winding, the active shield windings having twoterminations, and one termination of each active shield is connected tothe primary quiet termination so that in operation correspondinglyadjacent terminations of the secondary winding and the active shieldwindings carry alternating voltages of the same polarity and sameamplitude.

Further, in some embodiments, the connection of the active shieldwindings to the primary quiet termination is done via an auxiliarywinding wound around one of the legs of the planar magnetic core, theauxiliary winding to induce a voltage into the active shield windingsdesigned to be of opposite polarity of the residual common mode noiseinjected from primary to secondary.

The shield in between the primary and secondary is traditionallyimplemented by an isolated one turn copper foil on which a connectionwire is electrically connected and said connection winding is furtherconnected to a quiet spot in primary such as primary ground or bulkvoltage, HV,100 as is depicted in FIG. 18. One turn copper shield,cannot follow the spirit of the application Ser. No. 16/732,240, filledon Dec. 31, 2019, which offer significant improvement over thetraditional one turn copper shield. The shielding technique used in saidpatent application is implemented by using a number of turns implementedby using several strands of wire in parallel. Ideally would be that theactive shield from said patent application to cover the entire windingarea of the bobbin. A large multiple strands of wire creates challengesin manufacturing. The most common and cost competitive is to use onlythree strands of wire. In order to cover the winding area of the bobbin,an increased number of turns may be required for the active shield. Anincreased number of turns for the shield will decrease the effectivenessof the shield due an increased impedance to the said quiet spot. Onepotential solution is to decrease the height of the bobbin but in thiscase the leakage inductance of the transformer will increase and willincrease the DC impedances of the windings by limiting the windingspace.

This patent application presents several embodiments in which thelimitations associated with the number of strands are addressed. In thispatent application we will use a novel concept referred in thisapplication as “partial shields”.

In FIG. 18 is presented the power train of a flyback converter composedby an input voltage source Vin, 128, a transformer structure TR, 129,which includes a magnetic core, and the transformer windings, such asthe primary winding 210, which is connected to the input voltage source,128, and to the primary switch 108, controlled by control signal ,106.The positive terminal of the Vin is also referred in the field as thebulk voltage, HV, 100. The flyback transformer contains also thesecondary winding 214 which is connected to an output rectifier meanssuch as diode Do,130. The output rectifier means can be also implementedby the use of a synchronous rectifier. In series with the rectifiermeans there is an output capacitor Co, 132, which has one terminalconnected to the output ground, 104. The other terminal of the outputcapacitor is further connected to the output load and that terminal isalso referred in this patent as output voltage, Vo, 133. The output loadit is connected between Vo, 133 and the output GND, 104.

The circuit configuration of the flyback converter presented in FIG. 18is referred in the field as a low side secondary rectifier. In thisconfiguration the dot termination of the secondary winding is placed tothe cathode of the rectifier means. The dots placed in the windings ofthe transformer represent the polarity of the windings. When a voltageis applied to a winding in a transformer with the positive polarity atthe dot, the rest of the winding will have a positive polarity inducedat the dot as well.

Embodiment #1, for low side output rectifier.

When the primary switch 108 turns on and off the voltage at the primarywinding terminal C1, swings in between zero voltage level to a highvoltage level which is Vin+N*Vo, wherein N is the turns ratio betweenthe primary winding 210 and the secondary winding 214 and Vo is thevoltage across the output capacitor Co, 132. The transitions betweenzero voltage and Vin+N*Vo is done with very high dV/dt which createsdisplacement current in between the primary winding and the secondarywinding via the parasitic capacitance between the primary winding andthe secondary winding.

The purpose for the shield winding is to shield the secondary windingfrom the displacement current injected by the primary winding. Thedisplacement current from the primary winding and shield winding willreturn to the primary ground, and for this purpose the shield windingsare connected to a quiet spot in primary such as input ground or the HVbulk, 100.

The largest voltage swing in the primary is at the connection going tothe primary switch 108. That connection in FIG. 18 is C1. The voltageswing decreases per each turn as it gets closer the other termination ofthe primary winding, becoming zero at the termination B1. In order toprotect the secondary wining, 214, from the displacement currentinjection from the primary winding, a first shield 218, is placedbetween the primary winding, 210, and the secondary winding, 214. Theshield 218 is designed to shield the secondary from the displacementcurrent coming form the section ,223, of the primary winding wherein thevoltage swing is the largest. Due to the limitation of the number ofparallel strands and the need to have a given number of turns in theshield 218, in a certain ratio with the secondary winding, 214, thewinding area of the shield, 222, will only partially cover the secondarywinding, 214.

The polarity of the shield is done in a such way that the shieldwinding, 218, will move with the same polarity as the secondary winding.However, the termination D1 of the shield winding, 218, is placed to aquiet spot which is the HV, 100. D1 can be also connected to the inputground, 102. The shield technique of FIG. 18 in this patent applicationit is similar with the one depicted in FIG. 5A, filled on December 31,2019, with the exception that the shield winding, 218 covers only aportion of the secondary winding ,214. Because of the partial coverage,the tunning of the number of turns in 218, will not have to follow themethodology of the patent application Ser. No. 16/732,240, wherein thenumber of turns in the shield is equal with the number of turns in thesecondary winding. In the present patent application, there is adeliberate mismatch in between the number of turns in the secondarywinding 214 and the shield winding, 218, in order to create displacementcurrent that is opposite a polarity and the same amplitude of a residualcommon mode noise injected from the primary winding to the secondarywinding.

The section of the secondary winding, 220, it is not covered by theshield 218. Another shield is placed to cover for that section, which isthe shield 216. The polarity of the shield 216, is the same as thesecondary winding in order for the shield winding and the secondarywindings to swing with the same polarity. One termination of the shield216 is connected to a quiet spot such as HV, which can be also theprimary ground. The winding in both shields, 218 and 216, swing with thesame polarity as the secondary wining. The shield 216 which is tight toa quit spot, via M1 terminal, overlaps with the termination R1 of thesecondary winding, which is also connected to a quiet spot, Vo. Thenumber of turns in 216 can be chosen to be the same as the secondarywinding in the area 220, wherein the shield 216 and secondary winding,214, overlaps. The partial shield 216 and the windings of the secondary,214, contained in the area 220, can function as per main embodiment ofthe patent application Ser. No. 16/732,240, wherein the shield windingand the secondary winding swing with the same polarity and amplitude.Due to the fact that the termination D1 of the shield 218 is placed to aquiet spot and the adjacent winding in the secondary, 214, do have avoltage swing, a controlled noise injection is necessary in order tosignificantly reduce the displacement current between the secondarywining 214, and the shield winding 218. One solution is to have thenumber of turns in the shield 218 different than the number of urns inthe secondary wining contained in the winding area 222. The differenceof the number of turns between the shield 218 and the number of turns ofthe secondary wining contained in the winding section 222, creates amethod of tunning the displacement current in between primary andsecondary to be in opposite a polarity of a residual common mode noiseinjected from the primary winding to the secondary winding. Anothermethod of noise cancellation is by tunning the number of turns in theshield 216, which can be chosen to be different from the number of turnsfrom the secondary winding wound in the winding area 220 with thepurpose that the displacement current between primary and secondary tobe in opposite as polarity and the same amplitude of a residual commonmode noise injected from the primary winding to the secondary winding.

In embodiment #1 of this invention, two independent shields are placedin between the primary and secondary, each one covering a section of thebobbin. Both said shields have windings swinging with the same polarityas the secondary winding, and by tailoring the number of turns in eachsaid independent shields a displacement current is injected in betweenthe primary and the secondary, having an opposite polarity and the sameamplitude of a residual common mode noise injected from the primarywinding to the secondary winding.

Embodiment #2, for high side output rectifier.

In FIG. 19 is depicted a winding arrangement in a flyback transformerTR, 329, in a high side rectifier configuration, using two partialshields. The first partial shield, 318, is placed between the primarywining and secondary winding, said partial shield covering the section323, of the primary winding and the area 322 of the secondary winding.The area 323, of the primary wining is the area which has the largestvoltage swing in the primary winding, because is connected to the mainswitch, 108. The partial shield 318 is connected with the dot endtermination, E2 to the primary ground 102. The other termination D2 ofthe first partial shield 318, is not connected. The secondary winding314, has the dot at the termination P2, which is also connected to aquiet spot which is output ground 104. The partial shield winding 318and the secondary winding 314, has the windings with the same voltageswing polarity. The terminal E2 of the shield 318, is connected to aquiet spot, the input ground and the terminal P2 of the secondary winingis also connected to a quiet spot which is the output ground 104. Bothwindings, 318 and 314 have the dot connected to a quiet spot and theseterminals are adjacent to each other.

The second partial shield 316, has the dot termination L2, which isconnected to a quiet spot HV, 100. The second termination M2 is notconnected. The second shield does cover the winding area 320 of thesecondary winding 314.

Due to the fact that the termination L2 of the shield 316 is placed to aquiet spot and the adjacent winding in the secondary, 314, does have avoltage swing, a displacement current will occur in between the shield316 and the secondary winding 314. As a result, a controlled noiseinjection is necessary in order to significantly reduce the totaldisplacement current between the secondary winding 314 and primaryground. One solution is to have the number of turns in the shield 318different than the number of urns in the secondary wining contained inthe winding area 322. The difference of the number of turns between theshield 318 and the number of turns of the secondary wining contained inthe winding section 322, is a method of tunning the displacement currentin between primary and secondary to be in opposite a polarity and thesame amplitude of a residual common mode noise injected from the primarywinding to the secondary winding. The number of turns in the shield 316,can be also chosen to be different from the number of turns from thesecondary winding wound in the winding area 320 with the purpose thatthe displacement current between primary and secondary to be in oppositeas polarity and the same amplitude of a residual common mode noiseinjected from the primary winding to the secondary winding.

In embodiment #2 of this invention, two independent shields are placedin between the primary and secondary, each one covering a section of thebobbin. Both said shields have windings swinging with the same polarityas the secondary winding, and by tailoring the number of turns in eachsaid independent shields a displacement current is injected in betweenthe primary and the secondary, having an opposite polarity and the sameamplitude as the residual common mode noise injected from the primarywinding to the secondary winding.

Embodiment #3, for a low side output rectifier.

In FIG. 20 is depicted a winding arrangement in a flyback transformerTR, 429, in a low side rectifier configuration, using two partialshields. The first partial shield, 418, is placed between the primarywining and secondary winding, partial shield covering the section 423,of the primary winding and the area 422 of the secondary winding. Thearea 423, of the primary wining is the area which has the largestvoltage swing in the primary winding, because is connected to thetermination C3, which is connected to the main switch, 108. The partialshield 418 has the dot end termination, E3, not connected. The othertermination D3 is connected to the quiet spot, HV, 100. The secondarywinding 414, has the dot at the termination P3, which is connected tothe cathode of output diode Do, 130. The partial shield winding 418 andthe secondary winding 414, has the windings with the same voltage swingpolarity. The terminal D3 of the shield 418, is connected to a quietspot, the HV, 100, at the terminal D3. Both windings, 418 and 414 havethe non-dot connected to a quiet spot and these terminals are notadjacent to each other. As a result, a displacement current will beinjected in between the secondary winding, 414 and the HV, 100, which ispart of the primary. In addition to that there is another displacementcurrent between the primary winding 410, and the area of the secondarywinding, 420, which is not covered by a shield.

There is another shield 416, which covers the secondary winding over thearea 520, which is not in between primary and secondary winding, as aresult the winding 416, does not play the role of a shield. The winding416 acts not as a shield but as a controlled noise injection. The noiseinjected by the winding 416, has the role of injecting a displacementcurrent in between the secondary winding and the primary which is to bein opposite as polarity and the same amplitude as the residual commonmode noise injected from the primary winding to the secondary winding.In conclusion in this embodiment of the invention, here is a partialshield in between the noisiest section of the primary winding, 423, ofthe primary and the section 422 of the secondary winding. There is not apartial shield in between the primary winding 410, and the secondarywinding 414, in the winding area 420 of the secondary winding. As aresult, a displacement current will occur in between the secondarywinding in the area 420 and the primary winding in the area of 421. Tocompensate for this displacement, current a controlled noise injectionis produced by the winding 416, with the purpose to produce adisplacement current between primary and secondary to be in opposite aspolarity and the same amplitude as the residual common mode noiseinjected from the primary winding to the secondary winding.

In embodiment #3 of this invention, one independent shields is placed inbetween the primary and secondary to cover the section of the primarywith the largest voltage swing which is connected to the primary switch.Another noise injection winding is placed above the secondary winding inthe area not covered by the first partial shield, but not in between theprimary and secondary but above the secondary winding. Said noiseinjection winding is tailored to inject a displacement current betweenprimary and secondary winding, said displacement current having anopposite polarity and the same amplitude as the residual common modenoise injected from the primary winding to the secondary winding.

Embodiment #4, for a high side output rectifier.

In FIG. 21 is depicted a winding arrangement in a flyback transformerTR, 529, in a high side rectifier configuration, using two partialshields. The first partial shield, 518, is placed between the primarywinding and secondary winding, partial shield covering the section 523,of the primary winding and the area 522 of the secondary winding. Thearea 423, of the primary wining is the area which has the largestvoltage swing in the primary winding, because is connected to thetermination C4, which is connected to the main switch, 108. The partialshield 518 is connected with the dot end termination, to the inputground. The other termination D4 is not connected. The secondary winding514, has the dot at the termination P4, which is connected to a quietspot which is output ground. The partial shield winding 518 and thesecondary winding 514, has the windings with the same voltage swingpolarity. Both terminations at the dot end of the first partial shieldwinding 518 and the secondary winding 514 are connected to a quiet spot,in primary, the input ground and a quiet spot in the secondary, outputground 104. Both windings, 518 and 514 have the dot connected to a quietspot and these terminals are adjacent to each other. As a result, nodisplacement current will be injected in between the secondary winding,514 and the partial shield 518 in the event wherein the number of turnsin the partial shield 518 and the number of turns in the secondarywinding covered by the area 522 is the same. The number of turns in thepartial shield 518 and the number of turns in the secondary windingcovered by the partial shield, can be controlled in such way that thedisplacement current can be generated, to suppress the total common modenoise between primary and secondary.

There is another displacement current between the primary winding 510,and the area of the secondary winding, 514, which is not covered by ashield 518 which has to be cancelled.

There is another partial shield 516, which covers the secondary windingover the area 620, which however it is not in between primary andsecondary winding, as a result the winding 516, does not play the roleof a shield. The winding 516 acts not as a shield but as a controllednoise injection. The noise injected by the winding 516, has the role ofinjecting a displacement current in between the secondary winding andthe primary which is to be in opposite as polarity and amplitude of aresidual common mode noise injected from the primary winding to thesecondary winding. In conclusion in this embodiment of the inventionthere is a partial shield, 518, in between the most noisy section of theprimary winding, 523, of the primary and the section 522 of thesecondary winding, 514. There is not a partial shield in between theprimary winding 510, and the secondary winding 514, in the winding area520 of the secondary. As a result, a displacement current will occur inbetween the secondary winding in the area 520 and the primary winding inthe area of 421. To compensate for this displacement, current acontrolled noise injection is produced by the winding 416, with thepurpose to produce a displacement current between primary and secondaryto be in opposite as polarity and the same amplitude of a residualcommon mode noise injected from the primary winding to the secondarywinding.

In embodiment #4 of this invention, one independent shields is placed inbetween the primary and secondary to cover the section of the primarywith the largest voltage swing which is connected to the primary switch.Another noise injection winding is placed above the secondary winding inthe area not covered by the first partial shield, but not in between theprimary and secondary but above the secondary winding. Said noiseinjection winding is tailored to inject a displacement current betweenprimary and secondary winding having an opposite polarity and the sameamplitude as the residual common mode noise injected from the primarywinding to the secondary winding.

Embodiment #5, for a high side output rectifier and interleaved primaryand secondary winding.

In FIG. 22 is depicted a winding arrangement in a flyback transformerTR, 629, in a high side rectifier configuration, using two partialshields and wherein the secondary winding is contained between twosection of the primary, structure which is referred in this patentapplication as interleaved configuration. The first partial shield, 118,is placed between the primary wining and secondary winding, partialshield covering the section 120, of the secondary winding. The partialshield, 118 is placed in between the section of the primary windingconnected to terminal C, further connected to the primary switch 108,section which has the largest voltage swing amplitude. The partialshield 118 is connected with the dot end termination to a quiet spotwhich is the HV, 100, of the input voltage source, Vin, 128. The othertermination of the partial shield 118, E is not connected. The secondarywinding 114, has the dot at the termination connected to a quiet spotwhich is output ground, 104. The partial shield winding 118 and thesecondary winding 114, has the windings with the same voltage swingpolarity. Bothe terminations at the dot end of the first partial shieldwinding 118 and the secondary winding 114 are connected to a quiet spot,in primary, the input ground and a quiet spot in the secondary, outputground 104. In the case the number of turns in the partial shield 118and the secondary winding under the area 120, are the same nodisplacement current will be injected in between the secondary winding,114 and the partial shield 118 .By tunning the number of turns in thepartial shield 118 and the number of turns in the secondary windingcovered by the partial shield, the area 120, some controlleddisplacement current can be injected, this representing one method oftotal common mode noise suppression between primary and secondary.

There is another displacement current between the primary winding 110,and the area of the secondary winding, 122, which is not covered by ashield 118. In that area, displacement current will be injected inbetween the primary winding 110 and secondary winding 114.

There is another shield 116, which covers the secondary winding over thearea 124. The winding 116 acts as a shield in between the primarywinding 112, and the secondary winding 114, but also as a controllednoise injection. The noise injected by the winding 116, has the role ofinjecting a displacement current in between the secondary winding andthe primary which is in opposite as polarity and the same amplitude of aresidual common mode noise injected from the primary winding to thesecondary winding. In conclusion in this embodiment of the inventionthere is a partial shield in between the noisiest section of the primarywinding, 523, of the primary and the section 120 of the secondarywinding. In this embodiment there are two partial shields in between theprimary and secondary, a first shield 118, designed to shield thesecondary from the primary winding section which has the largest voltageswing amplitude, and a second shield 116 which shields the secondarywinding from another section of the primary winding, 112. The secondpartial shield 116, acts also as a noise injection, to inject in thesecondary winding 114 a displacement current in between the secondarywinding, a displacement current to be in opposite as polarity and thesame amplitude of a residual common mode noise injected from the primarywinding to the secondary winding.

In FIG. 23 is depicted the winding configuration in the bobbin using theembodiment #5. There are 22 turns in the primary winding formed by two11 turns per layer, 11 turns on the bottom layer and 11 turns on the toplayer of the bobbin. The bottom layer is connected to the primary switchand the top layer is connected to the HV, 100. In FIG. 23 is presentedalso the dual partial shield one on the layer 2 and one on the layer 4.

In FIG. 24 is depicted the electrical schematic of the transformer fromthe embodiment #5.

In embodiment #5 of this invention, a first partial shields is placed inbetween the primary and secondary to cover the section of the primarywith the largest voltage swing which is connected to the primary switch.Another partial shield is placed between the secondary winding in thearea not covered by the first partial shield. Said second partial shieldis tailored to inject a displacement current between primary andsecondary winding a current having an opposite polarity and the sameamplitude as the residual common mode noise injected from the primarywinding to the secondary winding.

A preferred embodiment is fully and clearly described above so as toenable one having skill in the art to understand, make, and use thesame. Those skilled in the art will recognize that modifications may bemade to the description above without departing from the spirit of thespecification, and that some embodiments include only those elements andfeatures described, or a subset thereof. To the extent thatmodifications do not depart from the spirit of the specification, theyare intended to be included within the scope thereof.

What is claimed is:
 1. A system for reducing common-mode noise, thesystem comprising: a switch mode power supply including primary andsecondary sides, primary and secondary side grounds, an input voltagesource, a primary switch, a transformer, a core, and a power output,wherein the primary side and the secondary side each have a quiettermination wherein the voltage does not change with respect to theprimary side ground and with respect to the secondary side ground; thetransformer includes a primary winding on the primary side connected tothe input voltage source via the primary switch, a secondary winding onthe secondary side connected to the power output via a rectifier means,and a partial shield winding placed between the primary and secondarywinding, wherein the partial shield winding has two terminations, iswound in the same direction as the secondary winding and overlaps onlypartially over said secondary winding; the partial shield winding andsecondary winding each have a number of turns; and one of the twotermination of the partial shield winding is connected to a quiettermination of the primary side, so that the termination of thesecondary winding and the partial shield winding that are adjacent eachother carry alternating voltages of a same polarity and a sameamplitude.
 2. The system of claim 1, wherein the number of turns of theactive shield is the same as the number of turns of the secondarywinding.
 3. The system of claim 1 wherein the number of turns of thepartial shield winding is different from the number of turns of thesecondary winding, so as to induce a voltage into the secondary windingwhich has a polarity that is opposite a polarity of a residual commonmode noise injected from the primary winding to the secondary winding.